Re: [music-dsp] Can anyone figure out this simple, but apparently wrong, mixing technique?
>>Message: 1 >>Date: Sat, 10 Dec 2016 14:31:37 -0500 >>From: "robert bristow-johnson">>To: music-dsp@music.columbia.edu >>Subject: [music-dsp] Can anyone figure out this simple, but apparently >> wrong, mixing technique? > >>it's this Victor Toth >>article:?http://www.vttoth.com/CMS/index.php/technical-notes/68 and it >>doesn't seem to make sense to me. >> >>it doesn't matter if it's 8-bit offset binary or not, there should not be a >>multiplication of two signals in the definition. >>i cannot see what i am missing. ?can anyone enlighten me? Search for "automixer". The author is not mixing individual samples, he is using observed signal magnitudes (that have time constants associated with them) to determine desired signal magnitudes, and from those desired magnitudes he is calculating channel gains. At least I hope that's what he's doing. I implemented "Dugan" automixers while at Altec Lansing; also one or two of my own that addressed some of the Dugan shortcomings. Alas, they never made it to market. Greg = Opening your eyes does nothing if you forget to turn on the light. ___ dupswapdrop: music-dsp mailing list music-dsp@music.columbia.edu https://lists.columbia.edu/mailman/listinfo/music-dsp
Re: [music-dsp] Iterative decomposition of an arbitrary frequency response by biquad IIR
On Wed, 05 Mar 2014 12:11:23 -0500, Marco Lo Monaco wrote: Ciao Greg, any chances to download your paper somewhere? I am also interested in it :) Marco, I'm sending it to the email address listed in your message. Others, please send me email if you want copies. I receive Music-DSP in digest form, and frankly I don't always read the whole thing, so I might miss your request. Greg = Everybody has their moment of great opportunity in life. If you happen to miss the one you care about, then everything else in life becomes eerily easy. -- Douglas Adams -- dupswapdrop -- the music-dsp mailing list and website: subscription info, FAQ, source code archive, list archive, book reviews, dsp links http://music.columbia.edu/cmc/music-dsp http://music.columbia.edu/mailman/listinfo/music-dsp
Re: [music-dsp] crossover filtering for multiband application
On Tue, 26 Feb 2013 17:35:56 -0500, James C Chandler Jr wrote: The parallel config I'd been thinking about, inspired by your diagrams, would be slightly different-- For instance in your figure 8-7 Three-way crossover, substitute an AllPass2 for your LP2 in the Low output. And in your figure 8-10 Four-way crossover, substitute an AllPass2 for HP2 in the High output, and also substitute an Allpass2 for your LP2 in the Low output. I do not understand why you would want to do this. While it will provide you with your desired constant transition band slopes, the responses will no longer sum to allpass. The preliminary result (barring foolish mistakes)-- A parallel configuration using one fourth order highpass and one fourth order linkwitz riley lowpass for each midband, and one highpass in the high band, and one lowpass in the low band-- It does show symmetrical band skirts between the bandpass interior sections. They mix surprisingly flat, but not exactly so. There are slight deviations. It mixes together unity-gain at very high and very low frequencies but gradually accumulates about a half dB gain nearing the center of the audio spectrum. What you describe is exactly what I would expect with the LP filters and HP filters replaced by AP filters. On the other hand, trying a binary-tree with the same assortment of filters-- The binary-tree did not show perfectly symmetrical band skirts (as expected), though the skirts are fairly symmetrical. The big surprise-- This binary-tree with non-symmetrical band skirts-- It mixes ruler flat over the entire audio spectrum! That is non-intuitive and I want to experiment more with the spreadsheet to better understand it. It is non-intuitive, but it is mathematically correct. With the binary-tree crossover network, the mid-band gain of each bandpass section is almost the same but not quite. With the binary-tree crossover network, adjacent bands' gains at each crossover frequency are almost identical but not quite. However, the entire tree mixes flat anyway, at least in the spreadsheet. Interesting as I didn't expect it to work that way. That might be due to slight differences in the positioning of the cutoff frequencies -- are they *exactly* one octave apart? For most people's use of hard limiters as in-line effects, a multiband hard limiter might be a weird animal? Yes, very much so. I only used a limiter example because it was the simplest way to demonstrate my point about the effects at the crossover frequencies. I don't think I've ever actually seen a multiband limiter in practice. Because if a limiter has been inserted to avoid clipping in the broadband signal, then merely limiting each band could never guarantee absence of clipping after the bands are summed back together? Yes, but the same applies to a multiband compressor, to a lesser extent. What configuration makes sense to you, which would be transparent flat when dynamics are not applied, but would do the right thing to signals near crossover points? You'd have to run two parallel paths -- a traditional crossover that sums to unity gain, to separate the audio signal; and a non-traditional bandsplitter in which the frequency bands overlap, for analysis of the audio signal. The configuration is best described by example. Assume that two of your desired bands extend from 500 Hz to 1000 Hz, and from 1000 Hz to 2000 Hz. Your SEPARATION path might consist of a traditional Linkwitz-Riley crossover, in which case filter spanning 500-1000 Hz would be down 6 dB at 1000 Hz, and the filter spanning 100-2000 Hz would also be down 6 dB at 1000 Hz. But the bands in your ANALYSIS path would overlap, such that the 500-1000 Hz band would be at 0 dB at 1000 Hz and attenuate as steeply as possible above that frequency. Similarly, the 1000-2000 Hz band would be at 0 dB at 1000 Hz and attenuate as steeply as possible below that frequency. You would use the output from the ANALYSIS path as a sidechain to determine gains to be applied to signals in the SEPARATION path. Afterward, you would recombine the signals in the SEPARATION path. One alternative that comes to mind is to use a separate non flat crossover network to drive the side chain, so that levels are sensed in a more realistic fashion near the crossover points? Exactly. Also, with fourth-order linkwitz riley bands, a crossover network with NUMEROUS fairly narrow bands would not show as much crossover point amplitude error, compared to a multiband compressor with a small number of wide bands? Whether that is troublesome is a judgment call. Greg = Everybody has their moment of great opportunity in life. If you happen to miss the one you care about, then everything else in life becomes eerily easy. -- Douglas Adams -- dupswapdrop -- the music-dsp mailing list and website: subscription info, FAQ, source code archive, list archive, book reviews, dsp links http://music.columbia.edu/cmc/music-dsp
[music-dsp] crossover filtering for multiband application
I am coming-in late on this discussion, so please forgive me if I miss the point entirely, but it appears that there is some confusion about the use of allpass compensation filters in Linkwitz-Riley crossovers. Ok, I have some interesting results, with 3-band and 4-bands constructed in following fashion: split freqencies S1, S2: S1 - LPFa, HPFb, APFc S2 - APFa, LPFb, HPFc --\-P-LPFa-APFa-\(P = processing) \-P-HPFb-LPFb-\ \-P-HPFc-APFc-+- split freqencies S1, S2, S3: S1 - LPFa, HPFb, APFc, APFd1 S2 - APFa1, LPFb, HPFc, APFd2 S3 - APFa2, APFb, LPFc, HPFd --\-P-LPFa-APFa1-APFa2-\ \-P-HPFb-LPFb-APFb---\ \-P-HPFc-LPFc-APFc---\ \-P-HPFd-APFd1-APFd2-+- Surprising to me was the discovery that frequency of APFs are significant, and from what I tried the setting above worked the best - taking freqencies of the other splits. This works very well in most cases, however there is now a slight boost when the splits are very near: http://i.imgur.com/nYOXkTi.jpg The APFs are constructed as I described by the resources linked by Joshua - a LR4 with no processing, and for all filters Q = 0.7071. This results are an improvement, and give an idea how to make a geneneral n-band crossover (though using n*(n-1) filters), however if anyone knows how to avoid the slight boost, or can explain about the APF frequencies and Q, or has different ideas how to do this altogether, please share. First, allow me to reference Active Realization of Multiway All-Pass Crossover Systems by Joseph A. DÂ’Appolito; Journal of the Audio Engineering Society, Volume 35, Number 4, April 1987, which explains the need for the allpass compensation. Next allow me to direct you to pages 8-11 through 8-21 (and particularly the bottom of page 8-20; Sum-to-Allpass Characteristics of Linkwitz-Riley Crossovers) of http://www.electrovoice.com/downloadfile.php?i=971398 (big download -- 13 MB). Regarding the frequencies and quality factors (Q) of the allpass filters; they can be determined from the sums of the lowpass and highpass transfer functions of the particular Linkwitz-Riley crossover in use. For example, a 2nd-order LR crossover has (normalized freq): 1 Hlp = s^2 + 2s + 1 -s^2 Hhp = s^2 + 2s + 1 Add them together and you have: 1 - s^2 -(s^2 - 1)-(s-1)(s+1) -(s-1) Hlp+Hhp = = = --- = --; an allpass filter. s^2 + 2s + 1 s^2 + 2s + 1(s+1)(s+1)(s+1) Similar analysis can be performed for higher-order LR crossovers. I hope that this is actually helpful; as I said I came to the party late so it might have already been discussed. Greg Berchin = Everybody has their moment of great opportunity in life. If you happen to miss the one you care about, then everything else in life becomes eerily easy. -- Douglas Adams -- dupswapdrop -- the music-dsp mailing list and website: subscription info, FAQ, source code archive, list archive, book reviews, dsp links http://music.columbia.edu/cmc/music-dsp http://music.columbia.edu/mailman/listinfo/music-dsp
Re: [music-dsp] ITU 1770 RLB filter coefficients and biquad IIR filter
On Wed, 16 Jan 2013 06:07:51 -0500, robert bristow-johnson wrote: if i were to try to re-calculate the coefficients, i would first factor out the constant gain, then factor both numerator and denominator into discrete-time poles and zeros. then map those poles and zeros back to analog poles and zeros using, i suppose the inverse bilinear transform (with warping). then re-transform back with the bilinear transform with the new sampling rate. i dunno. that's how i might approach it. I just caught the tail end of this thread, so forgive me if this has been mentioned before, but Frequency Domain Least Squares (FDLS) is perfect for this application. Original IEEE article is available at http://ieeexplore.ieee.org/xpl/login.jsp?tp=arnumber=4049924url=http%3A%2F%2Fieeexplore.ieee.org%2Fiel5%2F79%2F4049870%2F04049924, or directly from me. MATLAB code is available from IEEE; your choice of MATLAB or C++ code is available directly from me. Greg Berchin gjberchin (at) charter (dot) net (note that Reply-To: field is corrupted) = Everybody has their moment of great opportunity in life. If you happen to miss the one you care about, then everything else in life becomes eerily easy. -- Douglas Adams -- dupswapdrop -- the music-dsp mailing list and website: subscription info, FAQ, source code archive, list archive, book reviews, dsp links http://music.columbia.edu/cmc/music-dsp http://music.columbia.edu/mailman/listinfo/music-dsp